Understanding Trace Impedance

Thursday, February 7, 2019

Author: Donald Telian, SI Guys - Guest Blogger

The way high-speed signals interact with trace impedance has changed a bit over time, making the subject worthy of our attention. Thankfully, the importance - and even mechanics - of proper trace impedance is widely understood and agreed upon. So much so, the concept almost seems mundane – particularly against the rising importance of proper via impedance. However, I have found that engineers can benefit by improving their trace impedance intuition. For example if my trace impedance is low, should I make my trace thinner or wider? And if I can’t do that, should I move it closer to or further from ground? And do single-ended and differential signals interact with trace impedance in the same way? Not sure? Let’s have a look.

Capacitance and Impedance Intuition

Impedance intuition is readily acquired through two simple equations. Trace impedance “Z” is directly related to trace inductance (L) and capacitance (C), or Z=sqrt(L/C). While I’ve met a few who prefer to look at things inductively, the majority of us find capacitance simpler to grasp. In the realm of PCB traces, the terms in the common approximation for Capacitance (C=εA/d) are easily transferred to trace construction and simple to visualize. In the equation, “d” is a trace’s distance to ground, “A” is the area or size of the trace (i.e., its width), and “ε” is the dielectric constant of the surrounding material. Keeping this equation in mind impedance intuition follows, allowing you to predict the effects physical changes will have on impedance. Just keep in mind the inverse relationship between capacitance and impedance. In other words, as “C” goes up “Z” goes down, and vice versa.
So let’s try a few examples. Say I need to make traces thinner to route through a dense area, will the impedance go up or down? In this case “A” decreases causing “C” to decrease as well, resulting in an increase in “Z” or a higher impedance. Or what if production wants to swap in some modern materials that have a lower dielectric constant #8220;ε”? Once again, capacitance goes down so impedance goes up. As both these common occurrences have raised impedance, is there something I can do in the stackup to lower impedance back to where I want it? You guessed it, manipulate “d” which is the trace’s distance to ground. Indeed, if I decrease “d” then “C” increases causing “Z” to go down. See how that works? If you keep the capacitance equation around, it will be simpler to keep an eye on maintaining trace impedance when you trade-off common PCB parameters.

Typical Trace Impedances

Taking the capacitance equation (C=εA/d) forward, we might expect trace impedance to scale inversely with dielectric constant “ε” if we hold the ratio of trace width and distance to ground constant (A/d). Figure 1 shows this is generally true. Spanning the range of common dielectric constants (on the X axis), we note that trace impedance (on the Y axis) decreases ~linearly. The upper cluster of lines are microstrip (outer layer trace, ground on one side) impedances, varied by constant H=W (Height=Width, or d=A) values in mils. The lower cluster shows stripline (inner layer trace, grounds on both sides, hence two heights “H”) impedances, again with a constant A/d ratio.

Figure 1: How Trace Impedance Scales with Dielectric Constant

Figure 1: How Trace Impedance Scales with Dielectric Constant

Figure 1 also reveals that microstrip traces are not as amenable to 50 Ohms. That’s not too problematic because the use of microstrip is decreasing; it is primarily used for short connections from components to vias. Long microstrip routes are avoided for a variety of reasons, such as:
  • Component density leaves little room for routing on outer layers 
  • Fabrication parameters such as pre-preg thickness and etch angle are harder to control
  • Noise radiating from outer layer traces is not shielded by ground

Differential Traces

As serial links became the high-speed interconnect of choice, PCB traces became predominately “differential”. In practice, signal connections now required two routes instead of one; and that changes the impedance situation a bit. Furthermore, there are some differences in how trace impedance interacts with differential and/or single-ended signaling we need to be aware of.
Differential traces came into the mainstream for a number of good reasons. If you think about it, all signals are in a sense “differential”, because the logic level they transmit is always referenced to something – typically “ground”. As voltage swings decreased and “ground” became less consistent between components, PCBs, and systems, signals began to carry their own reference – or the other side of a differential “pair”. At the same time, single-ended signals became more fragile as the criticality and complexity of their design escalated and their margin to “reference” eroded.
Other reasons typically cited for differential signaling are decreases in crosstalk, power/ground rail noise, and EMI. Some of these attributes relate to the fact that a diff-pair often couples more to itself then its ground reference and/or neighboring signals – although some diff-pairs are implemented with wide gaps making them uncoupled or loosely coupled. And differential pairs are certainly better for long-distance connections.
The differential impedance of an uncoupled diff-pair is two times the trace’s single-ended impedance, and is typically specified to be 100 Ohms or 85 Ohms. Impedance-wise, the thing to remember is that as spacing between the pair decreases the differential impedance also decreases. One way to think about that is to picture coupling increasing, increasing capacitance (“d” in C=eA/d decreasing), and hence impedance “Z” decreasing. This decrease can be substantial. For example, the differential impedance of 4 mil stripline traces with distant grounds can decrease 30 Ohms as the traces move closer together. However in practice, a 10 Ohm decrease is more common.

Fabrication Factors

PCB fabrication introduces a variety of factors that affect trace impedance. Etch angle (the way fabricated traces turn out to be trapezoids instead of rectangles) raises impedance because “A” and hence “C” go down, causing “Z” to increase. Outer-layer plating (and hence etch angle) and solder mask dielectric thicknesses vary as well – both issues causing more change in impedances than you might think. And the thickness of copper on your signal layers (½ ounce, 1 or 2 ounce) also affects impedance, albeit to a lesser degree.
Fiberglass weave effects, fabricator re-imaging, and pre-preg thickness variation also significantly affect impedance. These effects are discussed in more detail here.

Impedance and Loss

Serial links have forced us to pay attention to high-frequency loss in traces, while trace impedance gets set to a constant. Differential impedances typically target 100 Ohms, I’ve been amazed by how stable links perform across a wide range of trace impedance – as long as impedance discontinuities are managed. Figure 2 shows how chip-to-chip 15 Gbps channel performance is influenced primarily by loss, or the choice of a dielectric material’s Dissipation factor “Df” (red=0.2, blue=0.1, green=0.002 – sometimes called “loss tangent”). Even though the Tx and Rx impedances are 100 Ohms, eye heights (Y axis) are shown to almost constant against a +/- 20% tolerance in trace impedance (X axis). More impactful are material choices, which cause a 4x (blue) to 6x (green) increase in eye heights – even without any Tx or Rx equalization. Applying 30% Tx de-emphasis improves Df=0.2 performance 3x (light red, X markers) with no material change, demonstrating again the power of SerDes Equalization Settings, or SES.

Figure 2: 15 Gbps Eye Heights, Varying Trace Impedance and Dielectric Loss

Figure 2: 15 Gbps Eye Heights, Varying Trace Impedance and Dielectric Loss

To emphasize the relevance of material loss the channel used in Figure 2 had constant impedance, as might occur in a simple chip-to-chip connection of about 7”. As such, the only discontinuities occurred at the chip boundaries. Note that channel impedance discontinuities must be carefully managed to realize Figure 2’s immunity to trace impedance. In practice this can be difficult, however – depending on data rate – some discontinuities can be ignored.
Though differential serial links show some immunity to trace impedance, the relevance of trace impedance to proper voltage swings in single-ended signaling schemes (such as DDRx) cannot be overstated. Indeed, this is the dynamic that forced us to get good at modeling, designing and fabricating PCB traces 30 years ago. So whether you are managing discontinuities in serial links, or buffer/trace impedance trade-offs in DDRx, a working knowledge of trace impedance is essential; which brings us back to the importance of understanding PCB trace impedance, in practice.


While the concept of trace impedance has been with us throughout the digital signal integrity journey, its interaction with signaling schemes has changed somewhat. What hasn’t changed is the mechanics of trace inductance and capacitance, and hence impedance. Equation-based schemes to visualize how impedance changes against physical parameters are helpful.
SiSoft users working with DDRx buffer/termination/trace impedance choices can access a process and QSI-ready Kit that illustrates how to maneuver through the trade-offs, as well as more than a dozen implementation Kits targeting common memory interfaces. There are also numerous QCD-ready serial link Kits pre-configured to help you understand and apply relevant specifications to your particular implementation.
Donald Telian, SiGuys - Guest Blogger 2/7/2019

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